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112W Boost Driver for Long Strings of LEDs Using All Ceramic Capacitors

筆者: Jim Christensen, Strategic Applications Engineer

Abstract: This reference design uses the MAX16834 to create a high-powered LED driver for a very long string(s) of LEDs. The LED current is adjustable with a potentiometer, and can be set as high as 1.5A into as many as 20 LEDs (75V total). For long life, ceramic capacitors are used for both input and output decoupling.

This is a reference design for a 112.5W boost LED driver that uses the MAX16834 for long strings of LEDs. These long LED strings are commonly found in streetlights and parking garage lights.
Input voltage: 24VDC ±5% (at 1.49A)
VLED configuration: Two parallel strings. Each string consists of 19 WLEDs and a 5Ω resistor for current balancing. Current is 750mA per sting for a total of 1.5A into 75V.
Dimming: 50µs (min) on-pulse for up to a 200:1 dimming ratio with a 100Hz dimming frequency
Note: this design has been built and tested. However, detailed testing has not occurred and there may be nuances that have yet to be discovered.
Figure 1. The LED driver board.
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Figure 1. The LED driver board.
Figure 2. Schematic of the LED driver.
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Figure 2. Schematic of the LED driver.
Figure 3. Layout of the LED driver.
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Figure 3. Layout of the LED driver.
Figure 4. Bill of Materials.
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Figure 4. Bill of materials.
Figure 5. Design spreadsheet provides peak and RMS currents in the MOSFET and inductor. To get the spreadsheet for use in your design, contact your local Maxim sales office.
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Figure 5. Design spreadsheet provides peak and RMS currents in the MOSFET and inductor. To get the spreadsheet for use in your design, contact your local Maxim sales office.
Figure 6. Switching MOSFET voltage and current-sense resistor voltage.
Figure 6. Switching MOSFET voltage and current-sense resistor voltage.
Figure 7. Output voltage (AC coupled) and switching MOSFET current-sense resistor voltage.
Figure 7. Output voltage (AC coupled) and switching MOSFET current-sense resistor voltage.
Figure 8. Drain voltage risetime.
Figure 8. Drain voltage risetime.
Figure 9. Drain voltage falltime.
Figure 9. Drain voltage falltime.
Figure 10. LED voltage (AC coupled) and current ripple.
Figure 10. LED voltage (AC coupled) and current ripple.
Figure 11. LED voltage (AC coupled) and MOSFET current-sense voltage.
Figure 11. LED voltage (AC coupled) and MOSFET current-sense voltage.
Figure 12. Dimming pulse of ~150µs.
Figure 12. Dimming pulse of ~150µs.
Figure 13. Dimming pulse of ~50µs.
Figure 13. Dimming pulse of ~50µs.
Figure 14. OVP with open LED string.
Figure 14. OVP with open LED string.
Figure 15. Predicted inductor temperature rise. The calculator is available from Coilcraft® design support tools.
Figure 15. Predicted inductor temperature rise. The calculator is available from Coilcraft® design support tools.

Circuit Description

Overview

This reference design is for a high-voltage boost current source for very long strings of LEDs. Applications that use long LED strings include, but are not limited to, streetlights and parking garage lights. Long LED strings can be a very cost-effective way to drive LEDs. Also, since the LEDs will have exactly the same current, brightness variations are nicely controlled. This design has a 24V input, up to a 75V LED output, and drives 1.5A through the LED string (or strings, if paralleled). The measured input power is 115.49W and the output power is 111.6W for an efficiency of about 96.6%.

PCB

The printed circuit board (PCB) is a general-purpose two-layer board for MAX16834 boost designs (Figures 1 and 3). Some PCB features are optional and not populated in the tested design; they are indicated on the schematic (Figure 2) as "no-pop." The layout uses a ground island below the IC that is single point connected to the power ground for low-noise operation. The design also uses the TSSOP version of the IC, since many streetlight manufacturers will not have the equipment to properly solder the alternate package, a TQFN. Figure 4 shows a Bill of Materials for this design.

Topology

This design is for a 200kHz continuous-boost regulator. In Figure 5 the spreadsheet printout shows the RMS and peak currents in the MOSFET and inductor. Continuous designs have the advantage of lower MOSFET and inductor currents. However, since current flows through the output diode (D2) when the MOSFET (Q1) turns on, the reverse recovery losses in the output diode result in higher dissipation and possibly higher turn-off noise. Inspecting the circuit waveforms in Figure 6, you can see that the on-time of the MOSFET is about 3.4µs and the off-time is about 1.5µs for a 69% duty cycle. Once the MOSFET turns off, the drain voltage rises to the output voltage plus a Schottky diode drop.

MOSFET Drive

Because of the continuous design, the peak MOSFET and inductor currents are less than what they would be with a discontinuous design. However, since there is current through the MOSFET during turn-on and turn-off, the MOSFET experiences switching losses during both transitions. The MAX16834 drives the MOSFET hard enough for the switch to turn on in about 5ns and turn off in 10ns (Figures 8 and 9), thus keeping the temperature rise low. If EMI becomes a problem, change the series resistor, R5, on the MOSFET gate to adjust the switching times. If this action causes too much power dissipation, place a second MOSFET, Q2, in parallel with Q1 to reduce the temperature rise.

Output Capacitance

For the input and output capacitance, the driver uses ceramic capacitors. Ceramic capacitors are durable and small but have limited capacitance, especially with a 200V rating which this design needs. In Figure 5, the design spreadsheet indicates that the driver needs 5.4µF to meet the desired output ripple voltage; to reduce cost and space, this circuit uses four 1.2µF capacitors (4.8µF in total). Consequently, the output voltage switching ripple is 2.88V (Figures 10 and 11), resulting in a current ripple of 182mA. This is 12% of the output current, somewhat higher than the target of 10% but still acceptable.

Dimming

The MAX16834 is well suited for dimming. When the PWMDIM (pin 12) goes low, three things happen. First, the gate drive (NDRV, pin 15) of the switching MOSFET, Q1, goes low. This prevents the delivery of additional energy to the LED string. Secondly, the gate drive (DIMOUT, pin 20) of the dimming MOSFET, Q4, goes low, immediately curtailing the LED string current and holding the voltage on the output capacitors constant. Finally, to keep the compensation capacitance at a steady-state voltage, the COMP (pin 5) goes to high impedance. This ensures that the IC will start at the correct duty cycle immediately after PWMDIM returns high. Each of these actions allows for short PWM on-times, and thus, fairly high dimming ratios.
The main limitation to short on-times is the charge-up time of the inductor. Looking at Figures 12 and 13, you see that the current follows the DIM pulse very well. There is decay at the beginning of the current pulse which is due to the ramp-up time of the inductor (about 12µs or roughly 2–3 switching cycles). Looking at the waveforms, you see that it takes about 40µs to 50µs for the voltage to fully recover and settle. If the DIM on-pulse is any shorter than 50µs, the output voltage would still be in deficit at the start of the next off pulse. This can cause erratic behavior that will persist until the DIM duty cycle is increased. Therefore, under full load (1.5A), the DIM on-pulse should never be less than 50µs. This implies that at a DIM frequency of 100Hz, the dimming ratio is 200:1. The only way to reduce the minimum on-pulse requirement is to increase the output capacitance, which is expensive and not usually needed for general lighting. If you reduce the LED current, the minimum on-time will drop and the dimming ratio can be increased. Ceramic capacitors exhibit a piezoelectric effect and there is some audible noise during dimming. However, with proper circuit-board mounting techniques, you can minimize the noise.

OVP

In Figure 14, the LED string is opened and the overvoltage protection (OVP) circuitry of the MAX16834 shuts down the driver for about 400ms between retry attempts. The peak voltage of 107V is higher than the design of 83V because of overshoot, caused by the low-output capacitance and the energy stored in the inductor.

Adjustments and Various Other Inputs and Outputs

R15 is a linear potentiometer that can adjust the LED current to any level between 0A and 1.7A. The MAX16834 has an input (SNYC) for synchronizing the switching frequency of the controller, if needed. The UVEN input allows external control of the driver (On/Off). A low-impedance source on the REFIN input overrides the potentiometer setting and allows control of the driver current. For example, a buffered DAC in a microcontroller can control the LED current using REFIN. The FLT# output goes low during the presence of a fault (such as OVP). Once the fault is removed, the signal returns high; it is does not latch.

Temperature Rise

The measured efficiency was 96.63% (VIN = 24.01V; I_IN = 1.49A; PIN = 115.49W; VLED = 74.9V; I_LED = 1.49A; POUT = 111.60W). Due to the high efficiency of the circuit, the components of the driver remain cool. The hottest component is the dimming MOSFET, Q4, which has a temperature rise of 41°C. This temperature rise is due principally to the small PCB footprint, and can be improved if the copper area around the drain pad is increased. The inductor, which is large, has a temperature rise of 23°C, higher than the predicted 7°C (Figure 15). It is likely that the inductor absorbs some of the MOSFET heat, since they both share the same large copper pad.

Temperature Measurements

The following temperatures were measured using actual LED loads:
VIN: 24VDC  
Ambient: 16°C ΔT
L1: 39°C 23°C
D1: 51°C 35°C
Q1: 51°C 35°C
Q3: 57°C 41°C
IC: 33°C 17°C

Power-Up Procedure

  1. Attach a string of up to 20 LEDs between the LED+ post and LED- post with an ammeter in series to measure the current. (Note: parallel strings can be used if the forward voltages of the LEDs are matched and/or series balancing resistors are added.)
  2. Attach a 24V, 6A power supply between the VIN post and GND post.
  3. Insert a shunt on connector J2.
  4. Turn on the 24V power supply.
  5. Adjust R15 to set the current from 0 to 1.5A.
  6. If dimming is desired, attach a PWM signal (0V to 3.3V) between the DIM IN post and GND post.
  7. Adjust the PWM duty cycle as desired to obtain dimming.


Coilcraft is a registered trademark of Coilcraft, Incorporated.



関連製品
MAX16834 ハイサイドLED電流検出およびPWM調光MOSFETドライバ内蔵、ハイパワーLEDドライバ 無料
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© Jun 28, 2010, Maxim Integrated Products, Inc.
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APP 4669: Jun 28, 2010
リファレンス回路4669, AN4669, AN 4669, APP4669, Appnote4669, Appnote 4669