Keywords: operational amplifiers (op amps), DC limitations, highprecision applications
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DC Error Characteristics of an Op Amp and the Effect on HighPrecision Applications

A similar version of this article was published January 2014 in EDN.
In this article we discuss the effects of input referred errors on op amps. These errors include input bias current, input offset current, input offset voltage, CMRR, PSRR, and finite input impedance. In reality, all these errors will occur at the same time. We also explain why a designer should be wary that the opamp performance specifications described in the EC Table of a data sheet are only guaranteed for the conditions defined at the top of that table, unless otherwise noted as a specific characteristic. In reality, the effects of these DC errors change when the supply voltage, commonmode voltage range, and other conditions change.
We are all familiar with potential dangers around us, and we engineers tend to forget that there are also dangerous traps to avoid when designing. Let’s see how this affects op amps (Figure 1A and 1B).
Figure 1A. A roadside danger sign, warning of an automotive skid hazard under certain conditions (rain and snow); Figure 1B on the right is an opamp “alert sign,” constructed from data sheet parameters and the specifications, warning that the signal must be contained between the power and ground rails.
We start with two basic equations:
I_{B} = (I_{BP} + I_{BN})/2 …..  (Eq. 1) 
I_{OS} = I_{BP}  I_{BN} …..  (Eq. 2) 
where:
I_{B} is average input bias current flowing into input pins;
I_{BP} is input bias current flowing into the positive input;
I_{BN} is input bias current flowing into the negative input;
I_{OS} is the input offset current.
Input bias and input offset currents are two of the most critical characteristics in many precision amplifier applications; they affect the output with resistive and capacitive feedback. Many of the inverting, noninverting, summing, and differential amplifiers reduce to Figures 2A and 2B once their active inputs are set to zero. For this analysis, we set all input signals as zero to assess the effect of input currents on the output accuracy. We will analyze resistive feedback (Figure 2A) and capacitive feedback (Figure 2B) circuits separately.
Figure 2A. Operational amplifier with resistive feedback. Figure 2B. Operational amplifier with capacitive feedback. Example devices are the MAX9620 and MAX4238 op amps.
Applying the superposition theorem on Figure 2A yields:
V_{OUT} = (1 + R_{F}/R_{G}) × [(R_{F}//R_{G}) × I_{BN} – R_{P} × I_{BP}] ……  (Eq. 3) 
The following inferences can be made from Equation 3:
Depending on the level of precision needed in the application, we must make some careful choices for both passive component values and the op amp itself. This is the best way to nullify the effect of input bias current on output accuracy. Therefore, selecting R_{P} = R_{F}//R_{G} yields:
V_{OUT} =  (1 + R_{F}/R_{G}) × (R_{F}//R_{G}) × I_{OS} …..  (Eq. 4) 
Selecting R_{P} = R_{F}//R_{G} helps us reduce the output error in order of magnitude. But for highprecision applications where sensor interfaces are made with large gain (> 100V/V), it is still preferable to select lowinputoffsetcurrent op amps. Also, it is not always feasible to add R_{P}. Finally, both input bias currents and resistance sizing play important roles in output error. For these situations designers should select op amps with low inputbias current, low inputoffset voltage, a low speedtopower ratio, and high CMRR and PSRR, such as the MAX44260, MAX9620, and MAX4238.
Output error can be further reduced by choosing lower R_{F} and R_{G} which, in turn, increase the circuit’s power dissipation. A careful tradeoff between output error and power dissipation needs to be maintained when choosing the size of resistances.
We return now to Figure 2B. Voltages on both positive and negative inputs produce:
V_{IN+} = V_{IN} = R_{P} × I_{BP}  (Eq. 5) 
where V_{IN+} is the voltage at the noninverting input, and V_{IN} is the voltage at the inverting input.
Applying Kirchhoff’s current law on inverting input yields:
V_{IN}/R_{G} + I_{BN}  I_{C} = 0…..  (Eq. 6) 
We eliminate V_{IN} in Equation 6 by substituting Equation 5, which yields Equation 7 for input bias currents and current through a feedback capacitor:
I_{C} = (R_{G} × I_{BN}  R_{P} × I_{BP})/R_{G} …..  (Eq. 7) 
Now apply Michael Faraday’s capacitance law:
V_{C} = 1/C ƒI_{C} dt  (Eq. 8) 
where V_{C} is voltage across the capacitor, which is also V_{OUT}. Substituting Equation 7 into Equation 8 yields:
V_{OUT} = 1/(R_{G} × C) × Integral(R_{G} × I_{BN}  R_{P} × I_{BP})dt…..  (Eq. 9) 
Equation 9 provides the output voltage error in Figure 2B. To minimize this error, one can select R_{P} = R_{G}, and that reduces Equation 9 to:
V_{OUT} = 1/(C) × Integral(I_{OS}) dt …..  (Eq. 10) 
Since C and I_{OS} are relatively constant, integrating Equation 10 over time would yield:
V_{OUT} = I_{OS} × t/C …….  (Eq. 11) 
Equation 11 implies a voltage ramp that drives the op amp into saturation.
We will now explain the effect of input offset voltage on both the typical resistive and capacitive feedback in opamp circuits.
Figure 3A. Operational amplifier with resistive feedback. Figure 3B. Operational amplifier with capacitive feedback.
From Figure 3A, the output voltage error is:
V_{OUT} = (1 + R_{F}/R_{G}) × V_{OS} …..  (Eq. 12) 
where (1 + R_{F}/R_{G}) is DC noise gain. The bigger the resistances, the larger is the error.
From Figure 3B, we have I_{C} = IRG for op amps with negligible input bias current; for V_{IN} = V_{OS}, we have I_{C} = IRG = V_{OS}/R_{G}. Using Faraday’s capacitance law yields:
V_{OUT} = Integral(V_{OS}) dt/(R_{G} × C) …..  (Eq. 13) 
Again, if we integrate Equation 13 over time, the opamp output is saturated to either rail depending on the polarity of the V_{OS}.
An important conclusion can be made from Equations 12 and 13: for given values of passive resistances and capacitances, the offset voltage is the main contributor to the accumulated outputvoltage error.
It is time for an example. Thermal drift of offset voltage (TCVos) and input offset voltage play a very critical role in precision applications where temperature variation is common. To emphasize the significance of TCV_{OS} for an op amp in precision applications, we compare a typical op amp (maximum TCV_{OS} = 5µV/°C and maximum V_{OS} = 50µV) with the MAX9620 (maximum TCV_{OS} = 0.12µV/°C and maximum V_{OS} = 10µV). We can say that:
Maximum V_{OS}(T) = max V_{OS}(+25°C) + maximum TCV_{OS} × (T25°C)  (Eq. 14) 
Now we can use the MAX9620 op amp as an example. Assume that in a given application the temperature goes from room temperature (+25°C) to +125°C and that the maximum V_{OS} due to thermal drift is:
Maximum V_{OS}(T) = 10µV + 0.12µV/°C × (100°C) = 22µV ….  (Eq. 15) 
In contrast, an op amp with a 50µV maximum offset and 5µV/°C maximum TCV_{OS} yields:
Maximum V_{OS}(T) = 50µV + 5µV/°C × (100°C) = 550µV ….  (Eq. 16) 
These results show the importance of thermal drift for input offset voltage where high accuracy in applications is desired.^{2}
Finite commonmode rejection ratio (CMRR) in typical op amps degrades precision by introducing an offset voltage at the input. The higher the CMRR of the amplifier, the more insensitive it is to input offsetvoltage change over the rated input commonmode voltage. In applications where the input signal is very small, i.e., in the order of mV ranges, high CMRR is absolutely critical.
The CMRR of an amplifier is the ratio of differential gain (A_{DIFF}) to commonmode gain (A_{CM}). CMRR can also be expressed in terms of the change in the input offset voltage with respect to change in the input commonmode voltage (V_{CM}) by 1V. Therefore:
V_{OUT} = A_{DIFF} × [(V_{IN+}  V_{IN}) + A_{CM} × V_{CM}/A_{DIFF}]  (Eq. 17) 
Equation 17 can also be termed as:
V_{OUT} = A_{DIFF} × (V_{IN+}  V_{IN}) + A_{CM} × V_{CM} ……………….  (Eq. 18) 
Also:
CMRR = A_{DIFF}/ A_{CM} = delta (V_{CM})/delta(V_{OS})  (Eq. 19) 
Finite powersupply rejection ratio (PSRR) also plays an important role in introducing additional input offset voltage with respect to change in the powersupply voltage. A change in the powersupply voltage (V_{CC}) alters the operating points of internal transistors which, in turn, affects the input offset voltage. The higher the PSRR, the more insensitive the amplifier will be to the change in input offset voltage when the powersupply voltage is changed.
PSRR = delta (V_{CC})/delta (V_{OS})  (Eq. 20) 
The CMRR and PSRR specs provided in the Electrical Characteristics (EC) table of an amplifier data sheet are specified at a particular input commonmode voltage and powersupply voltage range, respectively, unless otherwise noted. The CMRR spec provided is not the same over the entire powersupply range, and the PSRR spec provided is not the same over the entire input commonmode range.^{3}
Finite input impedance (R_{IN}) of an op amp will form a voltagedivider with the source impedance (R_{S}) driving the amplifier and introducing gain error. Consequently, a very high input impedance on the order of tens of 10^{9} ohms is required to ensure negligible error.
In the above situation the amount of input signal (V_{IN}) that the amplifier sees from a source depends on the input impedance parameter defined as:
V_{IN} = V_{SOURCE} × [R_{IN}/(R_{IN}+R_{S})]………………………..  (Eq. 21) 
From Equation 18 if R_{IN} >>> R_{S}, then V_{IN} = V_{S}.
In conclusion, if DC errors like input offset voltage, input bias currents, and finite input impedance are not addressed, opamp measurements will simply not be accurate. That performance is not acceptable in highprecision applications where accuracy is paramount. It is also essential that designers understand the significance and limitations of the opamp performance specs defined in datasheet EC tables. Following the guidelines presented here, designers can select both the correct op amp and the right passive components with the correct configurations for their applications. Ultimately, using the best op amp for a design will eliminate opamp errors and ensure the highest accuracy possible.
References
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© Mar 12, 2015, Maxim Integrated Products, Inc. 
APP 5693: Mar 12, 2015
TUTORIAL 5693, AN5693, AN 5693, APP5693, Appnote5693, Appnote 5693 